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Logo of nihpaAbout Author manuscriptsSubmit a manuscriptHHS Public Access; Author Manuscript; Accepted for publication in peer reviewed journal;
Phys Rev Lett. Author manuscript; available in PMC 2013 November 25.
Published in final edited form as:
Published online 2012 June 28.
PMCID: PMC3839313

Passive Phase Noise Cancellation Scheme


We introduce a new method for reducing phase noise in oscillators, thereby improving their frequency precision. The noise reduction is realized by a passive device consisting of a pair of coupled nonlinear resonating elements that are driven parametrically by the output of a conventional oscillator at a frequency close to the sum of the linear mode frequencies. Above the threshold for parametric instability, the coupled resonators exhibit self-oscillations which arise as a response to the parametric driving, rather than by application of active feedback. We find operating points of the device for which this periodic signal is immune to frequency noise in the driving oscillator, providing a way to clean its phase noise. We present results for the effect of thermal noise to advance a broader understanding of the overall noise sensitivity and the fundamental operating limits.

The emergence of self-oscillation has a major scientific significance as a widespread phenomenon in physics, chemistry, and biology [1]. Oscillators are also extremely useful, frequently appearing as crucial elements in the electrical devices that surround us in our highly technological environment. Essentially, oscillators are devices generating a periodic signal at an inherent frequency, whose primary function is therefore to provide a time or a frequency reference. An ideal self-sustained oscillator is mathematically described as a limit cycle in the phase space of dynamical variables, or equivalently as a periodic solution of a set of autonomous differential equations, independent of an external time reference. The ideal oscillator can thus be described in terms of a steadily increasing phase variable corresponding to the phase space point advancing around the limit cycle, with a 2π phase change corresponding to a period of the motion. This phase is highly sensitive to additional stochastic terms, or noise, in the equations of motion, as the appearance of periodicity without an external time reference implies the freedom to drift along the phase direction. The stochastic phase dynamics lead to a broadening of the peaks in the power spectrum of the oscillator output, which are perfectly discrete in the ideal case [2,3], and to a degradation of the performance as a time or frequency reference [4]. Thus, an essential task in the design of a good oscillator is to reduce the effects of the noise, present in the system, on the oscillator phase.

In this Letter, we propose a general scheme to reduce, or even eliminate, the noise in the output of an oscillator by passing the signal through a second passive noise cancellation device, rather than manipulating the oscillator itself. It is therefore broadly applicable to enhance the performance of existing oscillator designs. It is also valuable from a basic physics perspective, eliminating the need to analyze the active resonator-amplifier feedback system: instead, the noise performance is mapped to a passive element, whose fundamental stochastic properties are more amenable to the powerful tools of statistical physics [5]. The context of our work is to use nano- or microscale resonators to build high precision oscillators as illustrated in Fig. 1, although our scheme applies more generally. The nano- or microelectromechanical systems (NEMS or MEMS) implementation shown in Fig. 1 consists of a pair of coupled resonating elements that are parametrically driven with a noisy frequency near the sum of their linear mode frequencies. As explained below, it produces a signal with reduced noise at a frequency near the difference of these linear frequencies. The generation of a two-frequency signal by parametric excitation at the frequency sum is called nondegenerate parametric excitation, a phenomenon that has been studied in mechanical systems [6], but is more common in the context of optical parametric oscillators [7], where our scheme also applies.

FIG. 1
(color online). An illustration of the phase noise cancellation scheme. An oscillator produces a signal with a noisy frequency around ω1 + ω2. This signal parametrically drives a pair of coupled NEMS or MEMS beams with a relative phase ...

The ability of an oscillator based on a nonlinear resonator to suppress phase noise was demonstrated by Yurke et al. [8], who studied a nonlinear beam resonator driven into self-oscillation through an active feedback loop, composed of an amplifier driven to saturation and a phase shifter. They showed that if the resonator is operated at the critical Duffing point, by applying the minimal drive required for making the amplitude vs frequency curve multivalued, and by choosing the phase shift in the feedback loop between the signal and the drive to be 2π/3, the noise in the phase of the fedback signal has no effect on the oscillator phase. This was understood in terms of the insensitivity of the resonator frequency to the drive phase at this specific operating point. Here, we generalize this understanding of noise reduction in the feedback oscillator, and show that in the present case the output phase noise due to phase noise in the drive may be eliminated by operating at any points for which the output frequency itself is insensitive to the drive frequency.

We initiate our analysis by modeling a pair of coupled resonators, like the ones shown in Fig. 1, by two dimensionless equations of motion

equation M1

with (n, k) = (1, 2) and (2, 1). For details on the use of such equations for modeling NEMS and MEMS devices see Lifshitz and Cross [9,10]. We only wish to highlight the following points. The resonators are taken to be identical, having a resonant frequency ω0, which has been scaled out, although considering different resonant frequencies would not qualitatively change our results. The nonlinearity of the resonators originates from both the elastic restoring force and damping mechanism. In micro- and nanoscale resonators the linear damping is typically weak, [sm epsilon] << 1, where 1/[sm epsilon] is the quality factor of the resonator, and correspondingly a small drive amplitude is sufficient to excite them. Accordingly, each resonator is parametrically excited with a drive amplitude [sm epsilon]hn. In this regime, we can focus on the slow-time modulation of the basic oscillatory motion of the in-phase and out-of-phase modes of the coupled resonators, described by a pair of complex equations for the corresponding mode amplitudes An(T), where T = [sm epsilon]t is a slow time scale. In the regime of strong coupling, where the linear mode splitting is much larger than the resonator bandwidth, these equations are

equation M2

equation M3

where equation M4 and equation M5 are the linear frequencies of the in-phase and out-of-phase modes, respectively, [sm epsilon]Ωp = ωpω1ω2 is the small difference between the drive frequency and the sum of the linear mode frequencies, and g = (h1h2)/2. Similar slow equations for pairs of coupled resonators were recently introduced to study chaotic dynamics [11] and to analyze the so-called bifurcation topology amplifier [12].

In magnitude-phase coordinates, An = anen, Eqs. (2) can be transformed into four dynamical equations for the variables a1, a2, Φ = ϕ1 + ϕ2, and Ψ = ϕ1ϕ2,

equation M6

equation M7

equation M8

equation M9

The right hand sides of these equations depend only on the three variables a1, a2 and Φ. The absence of a dependence on Ψ reflects the fact that Eqs. (2) are unchanged by the transformation (ϕ1, ϕ2) (ϕ1 + β, ϕ2β). This property of the nondegenerate response to parametric excitation is well known [13], and does not occur in the degenerate case, where ω1 = ω2, in which both phases are fixed, corresponding to oscillations that are locked to the phase of the drive. The fixed point solutions a1,0, a2,0, Φ0 of the three dynamical Eqs. (3a) and (3c) correspond to periodic orbits of Eqs. (2) with frequency Ω0/2, where Ω0 = f4(a1,0; a2,0; Φ0). The amplitudes and frequency of these solutions are shown in Fig. 2 as a function of the drive frequency for g = 10, η = 1, and a coupling Δ = 7, corresponding to a linear mode splitting of equation M10 2.87 in units of the resonance frequency ω0.

FIG. 2
The periodic solutions of Eqs. (2). (a) The squared mode amplitudes (the in-phase mode has the larger amplitude); (b) Twice the frequency of the periodic solutions. Solid and dashed lines are stable and unstable solutions, respectively. The parameters ...

We now demonstrate how the dynamics can be utilized to eliminate the phase noise of the driving oscillator. We model this noise as white noise of intensity FΩp in the frequency of the drive, replacing Ωp with Ωp + Ξp(T), and assuming that [left angle bracket]Ξp(Tp(T’)[right angle bracket] = FΩp δ(TT’). This noise causes the phase of the driving source Φp to diffuse as [left angle bracket]p(T + τ) − Φp(T)]2[right angle bracket] = FΩp |τ|. Additional noise in the amplitude of the drive signal can be suppressed by using a limiter or a highly saturated amplifier [8,14]. The output signal, which is obtained by mixing and filtering the response to this drive, is proportional to cos[(ω2ω1)t + Ψ(T)]. At the steady state of oscillation, the phase Ψ can be expressed as Ψ(T) = Ω0T + ψ(T), where ψ is the small stochastic perturbation induced by the noise Ξp. The phase perturbation ψ can be calculated by solving the linearized version of the polar amplitude Eqs. (3) spectrally, as was done for a single oscillator by Yurke et al. [3], or using the secular perturbation method of Demir et al. [3]. This gives diffusion of the phase of the output signal, with the variance of the phase difference growing linearly in time

equation M11

where the diffusion constant DΩp quantifies the sensitivity of the phase of the output signal to the noise Ξp in the drive frequency. This expression applies in the limit that the time τ is much longer than the decay time onto the limit cycle for the noiseless oscillator. This approximation corresponds to frequency offsets close to the oscillator frequency. This is the relevant regime to explore since the width of the oscillator spectral peak is typically narrower than that of the driven resonator, whose width is determined by the quality factor, which in turn sets the decay time. The phase diffusion induced by white drive-frequency noise corresponds to a Lorenzian spectral peak of the output signal with a width of DΩpFΩp times the resonator bandwidth [sm epsilon]ω0. Equation (4) is the expected result because after transients have decayed and the system has settled onto the limit cycle, the net effect of the stochastic dynamics is a Brownian motion of the free phase.

Without going into the details of the calculation, we note that the diffusion coefficient DN for a white noise source N in Eqs. (3) may be calculated as the squared scalar product of two vectors DN = (v[perpendicular] · vN)2. The vector v[perpendicular] captures the phase sensitivity of the system, through the Jacobian matrix of Eqs. (3) describing the linearized flow in the vicinity of the limit cycle. Specifically, it is the eigenvector of the transpose of this Jacobian matrix that corresponds to the zero eigenvalue. vN is the noise vector, whose nth entry is the term multiplying the noise source in the function fn(vN = (0, 0, 1, 0) for the current example since Ωp only appears in Eq. (3c) and it has a coefficient of magnitude one). This description of the diffusion coefficient is a simplification of the general approach described in Ref. [3] for systems in which motion along the limit cycle is described by a steadily advancing phase variable Ψ which does not affect the time evolution of the dynamical system, and thus the limit cycle is represented by a fixed point in all other variables. In terms of the current example, this reducibility of the dynamical system is expressed by the fact that Ψ does not appear on the right hand sides of Eqs. (3). In the more general case the corresponding vectors v[perpendicular] (t) and vN(t) are time dependant: they are periodic, having the period of the limit cycle, and the diffusion coefficient is given by the time average of their squared scalar product.

In systems such as the current one under consideration, calculating the zero mode of the transposed Jacobian matrix provides a way to calculate the phase diffusion that results from any white noise vector acting on a limit cycle. However, if the noise originates from fluctuations in some parameter of the equations p so that the noise vector is equation M12, the long-time phase diffusion is directly related to the dependence of the oscillation frequency on the parameter p through

equation M13

The second equality follows from a perturbation analysis of the change in frequency δΩp due to a small perturbation δp in the parameter p. Eq. (5) shows that to reduce the frequency stability degradation due to parameter noise we seek extremum points in the curves of the oscillation frequency vs the noisy parameter. This possibility of complete noise elimination is due to the reducibility of the dynamical description, which makes the two vectors used for calculating the diffusion coefficient constant in time. In this case, it is possible to tune a single parameter and make these vectors orthogonal [15].

We now apply the ideas of the previous paragraphs to our noise reduction setup, for which the noisy parameter is p = Ωp. Figure 2(b) shows an extremum we can exploit at the maximum of the frequency curve. By operating at this point, i.e., at the drive frequency equation M14, the effect of drive frequency noise on the phase diffusion is eliminated, as shown in Fig. 3, and the corresponding frequency spectrum is narrowed (to a sharp peak in the absence of other noise terms). It is also noteworthy that for the parameters used to plot the diffusion coefficient DΩp in Fig. 3, the frequency stability is also improved along most of the curve, since DΩp < 1, and thus the output frequency noise is less than input frequency noise. An examination of the different curves in the figure indicates that larger nonlinear damping makes equation M15 more accessible experimentally, since this increases the frequency separation between the maximum (dΩ0=dΩp = 0) and the saddle node (dΩ0=dΩp = ∞). It is possible to control the nonlinear parameters of a resonator (both Duffing and damping terms) by adding a parametric feedback loop, as we have recently shown elsewhere [16].

FIG. 3
Phase diffusion of the output signal induced by frequency noise of unit strength for different values η of the nonlinear damping. For each curve, equation M20 is the value of Ωp for which the diffusion is zero. Note that DΩp is also smaller ...

The ability of the device to clean phase noise is limited by the thermal noise floor. To discover this fundamental limit we add the complex thermal noise terms Ξn = ΞRn + iΞIn to each of Eqs. (2), with the individual noise components white, uncorrelated, and of the same intensity Fth. Our analysis shows that the phase diffusion resulting from thermal noise is then given by Eq. (4), but with the coefficients DΩpFΩp replaced by DthFth, where Dth is plotted in Fig. 4. In terms of the actual physical parameters, the lower phase diffusion limit is (kBT/Ec)Dth (in units of the bandwidth [sm epsilon]ω0) with kBT the thermal energy, equation M16 the potential energy of the resonator element when driven to the Duffing critical amplitude, equation M17 the Duffing nonlinearity parameter (in units of force per volume), and m the resonator mass (see Ref. [10]). Since thermal noise does not originate from some fluctuating parameter, it cannot be eliminated by finding extremum points in the dependence of the output frequency. Nevertheless, it is possible to lower the thermal noise limit by reducing Dth. The idea is based on the fact that the direct effect of thermal noise on the phase variable is reduced at large amplitudes, so in the large amplitude limit, the only cause of phase diffusion is the conversion of noise from the amplitude to the phase (AM-PM conversion). For a single oscillator, this conversion is completely eliminated by operating at a point for which the resonator frequency is insensitive to the amplitude [17], and this approach can be generalized to achieve amplitude-phase detachment in our system as well. At low enough temperatures the contribution of quantum noise to the phase diffusion becomes relevant, and can be calculated as it was done in [18].

FIG. 4
Thermal noise limit of the phase diffusion of the output signal, for Fth = 1 and the same parameters as in Fig. 2. The asterisk indicates the value at equation M21.

In conclusion, we have described a passive device that eliminates phase noise in oscillators. The device is made of two coupled resonators, driven parametrically in the non-degenerate mode by the output of a conventional oscillator. We find a driving frequency for which the resulting limit-cycle oscillation frequency is insensitive to the drive frequency and show that operating at this point eliminates the phase noise in the driving oscillator. We have discussed the operational limitation due to thermal noise, and have suggested ways to improve this limit. Along with the interesting physics it portrays, this device offers a practical way to handle the extensively studied, cardinal problem of oscillator phase noise.


This research was supported by DARPA through the DEFYS program.


PACS numbers: 05.45.−a, 62.25.−g, 84.30.−r, 85.85.+j


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